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U211B2/ b3 rev. a2, 14-apr-98 1 (21) phase-control circuit - general purpose feedback description the integrated circuit U211B2/ b3 is designed as a phase- control circuit in bipolar technology with an internal frequency-voltage converter. furthermore, it has an inter- nal control amplifier which means it can be used for speed-regulated motor applications. it has an integrated load limitation, tacho monitoring and soft-start functions, etc. to realize sophisticated motor control systems. features internal frequency-to-voltage converter externally-controlled integrated amplifier overload limitation with a afold backo characteristic optimized soft-start function tacho monitoring for shorted and open loop automatic retriggering switchable triggering pulse typ. 155 ma voltage and current synchronization internal supply-voltage monitoring temperature reference source current requirement 3 ma block diagram control amplifier load limitation speed / time controlled voltage monitoring supply voltage limitation reference voltage output pulse pulse-blocking tacho monitoring frequency- to-voltage converter = f (v 12 ) phase - control unit soft start 11(10) 12(11) 13(12) 9(8) 8(7) 18*) voltage / current detector automatic retriggering 17(16) 1(1) 4(4) 5*) 95 10360 v s gnd + v ref 6(5) 7(6) 3(3) 2(2) 16(15) 10(9) 14(13) 15(14) controlled current sink figure 1. block diagram (pins in brackets refer to so16) *) pins 5 and 18 connected internally order information extended type number package remarks U211B2-b dip18 u211b3-bfp so16 u211b3-bfpg3 so16 taped and reeled
U211B2/ b3 rev. a2, 14-apr-98 2 (21) 95 10361 r 3 220 k r 4 470 k r 2 v s 3.3 nf 1 m gnd c 1 22 25 v c 11 2.2 r 12 180 m r 1 18 k 1n4007 d 1 2 w tic 226 r 8 33 m 1 w r 11 2 m 100 k r 6 c 6 100 nf 10 /16v c 7 c 8 220 nf 22 k r 7 c 3 2.2 16 v c 5 1 nf r 5 1 k speed sensor c 4 220 nf l n 1 k r 10 r 9 1 m 4.7 /16v c 9 r 19 100 k c 10 2.2 /16v r 31 100 k r 14 56 k r 13 47 k v m = 230 v ~ control amplifier load limitation speed / time controlled voltage monitoring supply voltage limitation reference voltage output pulse pulse blocking tacho monitoring frequency- to-voltage converter phase- control unit soft start 15 14 11 10 12 13 9 8 7 3 2 16 18 voltage / current detector automatic retriggering 17 1 6 4 5 = f (v 12 ) + c 2 set speed voltage actual speed voltage f f f f f f controlled current sink v ref figure 2. speed control, automatic retriggering, load limiting, soft start
U211B2/ b3 rev. a2, 14-apr-98 3 (21) pin description 1 2 3 4 5 6 7 8 10 9 18 17 16 14 15 13 12 11 v s output 14842 retr v rp c p f/v i sync gnd v ref ovl i sense c soft ctr/opo op+ pb/tm v sync c rv op figure 3. pinning dip18 pin symbol function 1 i sync current synchronization 2 gnd ground 3 v s supply voltage 4 output trigger pulse output 5 retr retrigger programming 6 v rp ramp current adjust 7 c p ramp voltage 8 f/v frequency-voltage converter 9 c rv charge pump 10 op op inverting input 11 op+ op non-inverting input 12 ctr/opo control input / op output 13 c soft soft start 14 i sense load current sensing 15 ovl over load adjust 16 v ref reference voltage 17 v sync voltage synchronization 18 pb/tm pulse blocking / tacho monitoring v s output v rp c p f/v c rv i sync gnd 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 14843 ovl i sense c soft ctr/opo op+ op v sync v ref figure 4. pinning so16 pin symbol function 1 i sync current synchronization 2 gnd ground 3 v s supply voltage 4 output trigger pulse output 5 v rp ramp current adjust 6 c p ramp voltage 7 f/v frequency-voltage converter 8 c rv charge pump 9 op op inverting input 10 op+ op non-inverting input 11 ctr/opo control input / op output 12 c soft soft start 13 i sense load current sensing 14 ovl over load adjust 15 v ref reference voltage 16 v sync voltage synchronization
U211B2/ b3 rev. a2, 14-apr-98 4 (21) description mains supply the U211B2 is fitted with voltage limiting and can therefore be supplied directly from the mains. the supply voltage between pin 2 (+ pol/ ) and pin 3 builds up across d 1 and r 1 and is smoothed by c 1 . the value of the series resistance can be approximated using (see figure 2): r 1 v m v s 2i s further information regarding the design of the mains supply can be found in the design hints. the reference voltage source on pin 16 of typ. 8.9 v is derived from the supply voltage and is used for regulation. operation using an externally stabilized dc voltage is not recommended. if the supply cannot be taken directly from the mains because the power dissipation in r 1 would be too large, then the circuit shown in figure 5 should be used. 123 4 5 c 1 r 1 24 v~ ~ 95 10362 figure 5. supply voltage for high current requirements phase control there is a general explanation in the data book abipolar power control circuitso on the common phase control function. the phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains synchro- nized by the voltage detector) with the set value on the control input pin 12. the slope of the ramp is determined by c 2 and its charging current. the charging current can be varied using r 2 on pin 6. the maximum phase angle max can also be adjusted using r 2 . when the potential on pin 7 reaches the nominal value predetermined at pin 12, then a trigger pulse is generated whose width t p is determined by the value of c 2 (the value of c 2 and hence the pulse width can be evaluated by assuming 8 s/nf). at the same time, a latch is set, so that as long as the automatic retriggering has not been activated, no more pulses can be generated in that half cycle. the current sensor on pin 1 ensures that, for operations with inductive loads, no pulse will be generated in a new half cycle as long as a current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. this makes sure that agapso in the load current are prevented. the control signal on pin 12 can be in the range 0 v to 7 v (reference point pin 2). if v 12 = 7 v, the phase angle is at maximum = max i.e., the current flow angle is a minimum. the phase angle min is minimum when v 12 = v 2 . voltage monitoring as the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveillance. at the same time, all of the latches in the circuit (phase control, load limit regulation, soft start) are reset and the soft-start capacitor is short circuited. used with a switching hysteresis of 300 mv, this system guarantees defined start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply. soft-start as soon as the supply voltage builds up (t 1 ), the integrated soft-start is initiated. figure 6 shows the behaviour of the voltage across the soft-start capacitor and is identical with the voltage on the phase-control input on pin 12. this behavior guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time.
U211B2/ b3 rev. a2, 14-apr-98 5 (21) v c3 t v 12 v 0 t 1 t tot t 2 t 3 95 10272 figure 6. soft-start t 1 = build-up of supply voltage t 2 = charging of c 3 to starting voltage t 1 + t 2 = dead time t 3 = run-up time t tot = total start-up time to required speed c 3 is first charged up to the starting voltage v 0 with ta current of typically 45 a (t 2 ). by then reducing the charging current to approx. 4 a, the slope of the charging function is substantially reduced so that the rotational speed of the motor only slowly increases. the charging current then increases as the voltage across c 3 increases,resulting in a progressively rising charging function which accelerates the motor more and more strongly with increasing rotational speed. the charging function determines the acceleration up to the set-point. the charging current can have a maximum value of 55 a. frequency-to-voltage converter the internal frequency-to-voltage converter (f/v- converter) generates a dc signal on pin 10 which is proportional to the rotational speed using an ac signal from a tacho generator or a light beam whose frequency is in turn dependent on the rotational speed. the high- impedance input pin 8, compares the tacho voltage to a switch-on threshold of typ. 100 mv. the switch-off threshold is given with 50 mv. the hysteresis guarantees very reliable operation even when relatively simple tacho generators are used. the tacho frequency is given by: f n 60 p(hz) where: n = revolutions per minute p = number of pulses per revolution the converter is based on the charge pumping principle. with each negative half-wave of the input signal, a quantity of charge determined by c 5 is internally amplified and then integrated by c 6 at the converter output on pin 10. the conversion constant is determined by c 5 , its charge transfer voltage of v ch , r 6 (pin 10) and the internally adjusted charge transfer gain. g i i 10 i 9 8.3 k = g i c 5 r 6 v ch the analog output voltage is given by v o = k f the values of c 5 and c 6 must be such that for the highest possible input frequency, the maximum output voltage v o does not exceed 6 v. while c 5 is charging up, the r i on pin 9 is approximately 6.7 k . to obtain good linearity of the f/v converter, the time constant resulting from r i and c 5 should be considerably less (1/5) than the time span of the negative half-cycle for the highest possible input frequency. the amount of remaining ripple on the output voltage on pin 10 is dependent on c 5 , c 6 and the internal charge amplification. d v o = g i v ch c 5 c 6 the ripple d v o can be reduced by using larger values of c 6 . however, the increasing speed will then also be reduced. the value of this capacitor should be chosen to fit the particular control loop where it is going to be used. pulse blocking the output of pulses can be blocked using pin 18 (standby operation) and the system reset via the voltage monitor if v 18 1.25 v. after cycling through the switching point hysteresis, the output is released when v 18 1.5 v followed by a soft-start such as that after turn on. monitoring of the rotation can be carried out by connecting an rc network to pin 18. in the event of a short or open circuit, the triac triggering pulses are cut off by the time delay which is determined by r and c. the capacitor c is discharged via an internal resistance r i = 2 k with each charge transfer process of the f/v converter. if there are no more charge transfer processes, c is charged up via r until the switch-off threshold is exceeded and the triac triggering pulses are cut off. for operation without trigger pulse blocking or monitoring of the rotation, pins 18 and 16 must be connected together.
U211B2/ b3 rev. a2, 14-apr-98 6 (21) c = 1 f 10 v 95 10363 18 17 16 15 123 4 r = 1 m figure 7. operation delay control amplifier (figure 2) the integrated control amplifier with differential input compares the set value (pin 11) with the instantaneous value on pin 10 and generates a regulating voltage on the output pin 12 (together with the external circuitry on pin 12) which always tries to hold the actual voltage at the value of the set voltages. the amplifier has a transmittance of typically 1000 a/v and a bipolar current source output on pin 12 which operates with typically 110 a. the amplification and frequency response are determined by r 7 , c 7 , c 8 and r 11 (can be left out). for open-loop operation, c 4 , c 5 , r 6 , r 7 , c 7 , c 8 and r 11 can be omitted. pin 10 should be connected with pin 12 and pin 8 with pin 2. the phase angle of the triggering pulse can be adjusted using the voltage on pin 11. an internal limitation circuit prevents the voltage on pin 12 from becoming more negative than v 16 + 1 v. load limitation the load limitation, with standard circuitry, provides absolute protection against overloading of the motor. the function of the load limiting takes account of the fact that motors operating at higher speeds can safely withstand larger power dissipations than at lower speeds due to the increased action of the cooling fan. similarly, consider- ations have been made for shortterm overloads for the motor which are, in practice, often required. these behavior are not damaging and can be tolerated. in each positive half-cycle, the circuit measures via r 10 the load current on pin 14 as a potential drop across r 8 and produces a current proportional to the voltage on pin 14. this current is available on pin 15 and is integrated by c 9 . if, following high-current amplitudes or a large phase angle for current flow, the voltage on c 9 exceeds an internally set threshold of approximately 7.3 v (reference voltage pin 16), a latch is set and the load limiting is turned on. a current source (sink) controlled by the control voltage on pin 15 now draws current from pin 12 and lowers the control voltage on pin 12 so that the phase angle is increased to max . the simultaneous reduction of the phase angle during which current flows causes firstly: a reduction of the rotational speed of the motor which can even drop to zero if the angular momentum of the motor is excessively large, and secondly: a reduction of the potential on c 9 which in turn reduces the influence of the current sink on pin 12. the control voltage can then increase again and bring down the phase angle. this cycle of action sets up a abalanced conditiono between the acurrent integralo on pin 15 and the control voltage on pin 12. apart from the amplitude of the load current and the time during which current flows, the potential on pin 12 and hence the rotational speed also affects the function of the load limiting. a current proportional to the potential on pin 10 gives rise to a voltage drop across r 10 , via pin 14, so that the current measured on pin 14 is smaller than the actual current through r 8 . this means that higher rotational speeds and higher current amplitudes lead to the same current integral. therefore, at higher speeds, the power dissipation must be greater than that at lower speeds before the internal threshold voltage on pin 15 is exceeded. the effect of speed on the maximum power is determined by the resistor r 10 and can therefore be adjusted to suit each individual application. if, after the load limiting has been turned on, the momentum of the load sinks below the ao-momentumo set using r 10 , then v 15 will be reduced. v 12 can then in- crease again so that the phase angle is reduced. a smaller phase angel corresponds to a larger momentum of the mo- tor and hence the motor runs up - as long as this is allowed by the load momentum. for an already rotating machine, the effect of rotation on the measured acurrent integralo ensures that the power dissipation is able to increase with the rotational speed. the result is a current-controlled accelleration run-up which ends in a small peak of accel- leraton when the set point is reached. the latch of the load limiting is simultaneously reset. the speed of the motor is then again under control and is capable of carrying its full load. the above mentioned peak of acceleration depends upon the ripple of actual speed voltage. a large amount of ripple also leads to a large peak of acceleration. the measuring resistor r 8 should have a value which ensures that the amplitude of the voltage across it does not exceed 600 mv.
U211B2/ b3 rev. a2, 14-apr-98 7 (21) design hints practical trials are normally needed for the exact determination of the values of the relevant components in the load limiting. to make this evaluation easier, the following table shows the effect of the circuitry on the important parameters of the load limiting and summa- rizes the general tendencies. parameters component r 10 increasing r 9 increasing c 9 increasing p max increases decreases n.e. p min increases decreases n.e. p max / min increases n.e. n.e. t d n.e. decreases increases t r n.e. increases increases p max maximum continuous power dissipation p 1 = f (n) n 0 p min power dissipation with no rotation p 1 = f (n) n = 0 t d operation delay time t r recovery time n.e no effect pulse output stage the pulse output stage is short-circuit protected and can typically deliver currents of 125 ma. for the design of smaller triggering currents, the function i gt = f(r gt ) has been given in the data sheets in figure 18. automatic retriggering the variable automatic retriggering prevents half-cycles without current flow, even if the triac is turned off earlier, e.g., due to a collector which is not exactly centered (brush lifter) or in the event of unsuccessful triggering. if necessary, another triggering pulse is generated after a time lapse which is determined by the repetition rate set by resistance between pin 5 and pin 3 (r 5-3 ). with the maximum repetition rate (pin 5 directly connected to pin 3), the next attempt to trigger comes after a pause of 4.5 t p and this is repeated until either the triac fires or the half-cycle finishes. if pin 5 is connected, then only one trigger pulse per half-cycle is generated. because the value of r 5-3 determines the charging current of c 2 , any repetition rate set using r 5-3 is only valid for a fixed value of c 2 . general hints and explanation of terms to ensure safe and trouble-free operation, the following points should be taken into consideration when circuits are being constructed or in the design of printed circuit boards. the connecting lines from c 2 to pin 7 and pin 2 should be as short as possible. the connection to pin 2 should not carry any additional high current such as the load current. when selecting c 2 , a low temperature coefficient is desirable. the common (earth) connections of the set-point generator, the tacho generator and the final interference suppression capacitor c 4 of the f/v converter should not carry load current. the tacho generator should be mounted without influence by strong stray fields from the motor. the connections from r 10 and c 5 should be as short as possible. to achieve a high noise immunity, a maximum ramp voltage of 6 v should be used. the typical resistance r can be calculated from i as follows: r (k ) t(ms) 1.13(v) 10 3 c nf) 6(v) t = period duration for mains frequency (10 ms at 50 hz) c = ramp capacitor, max. ramp voltage 6 v and constant voltage drop at r = 1.13 v. a 10% lower value of r (under worst case conditions) is recommended.
U211B2/ b3 rev. a2, 14-apr-98 8 (21) 95 10716 v v gt v l i l /2 3/2 2 t p t pp = 4.5 t p mains supply trigger pulse load voltage load current figure 8. explanation of terms in phase relationship design calculations for mains supply the following equations can be used for the evaluation of the series resistor r 1 for worst case conditions: r 1max 0.85 v mmin v smax 2i tot r 1min v m v smin 2i smax p (r1max) (v mmax v smin ) 2 2r 1 where: v m = mains voltage v s = supply voltage on pin 3 i tot = total dc current requirement of the circuit = i s + i p + i x i smax = current requirement of the ic in ma i p = average current requirement of the triggering pulse i x = current requirement of other peripheral components r 1 can be easily evaluated from the figures 22 to 24.
U211B2/ b3 rev. a2, 14-apr-98 9 (21) absolute maximum ratings reference point pin 2, unless otherwise specified parameters symbol value unit current requirement pin 3 i s 30 ma t 10 s i s 100 ma synchronization current pin 1 pin 17 t 10 s pin 1 t 10 s pin 17 i synci i syncv i i i i 5 5 35 35 ma ma ma ma f/v converter pin 8 input current i i 3 ma t 10 s i i 13 ma load limiting pin 14 limiting current, negative half-wave i i 5 ma t 10 s 35 ma input voltage pin 14 pin 15 v i v i 1 ? v 16 ? to 0 v v phase control input voltage pin 12 v i 0 to 7 v input current pin 12 pin 6 i i i i 500 1 a ma soft-start input voltage pin 13 v i ? v 16 ? to 0 v pulse output reverse voltage pin 4 v r v s to 5 v pulse blocking input voltage pin 18 v i ? v 16 ? to 0 v amplifier input voltage pin 11 pin 9 open pin 10 v i v i 0 to v s ? v 16 ? to 0 v v reference voltage source output current pin 16 i o 7.5 ma storage temperature range t stg 40 to +125 c junction temperature t j 125 c ambient temperature range t amb 10 to +100 c thermal resistance parameters symbol maximum unit junction ambient dip18 so16 on p.c. so16 on ceramic r thja 120 180 100 k/w k/w k/w
U211B2/ b3 rev. a2, 14-apr-98 10 (21) electrical characteristics v s = 13.0 v, t amb = 25 c, reference point pin 2, unless otherwise specified parameters test conditions / pins symbol min. typ. max. unit supply voltage for mains operation pin 3 v s 13.0 v limit v supply voltage limitation i s = 4 ma pin 3 i s = 30 ma v s v s 14.6 14.7 16.6 16.8 v v dc current requirement v s = 13.0 v pin 3 i s 1.2 2.5 3.0 ma reference voltage source i l = 10 a pin 16 i l = 5 ma v ref 8.6 8.3 8.9 9.2 9.1 v v temperature coefficient pin 16 tc vref 0.5 mv/k voltage monitoring turn-on threshold pin 3 v son 11.2 13.0 v turn-off threshold pin 3 v soff 9.9 10.9 v phase-control currents synchronization current pin 1 i synci 0.35 2.0 ma pin 17 i syncv 0.35 2.0 ma voltage limitation i l = 5 ma pins 1 and 17 v i 1.4 1.6 1.8 v reference ramp , see figure 9 charge current i 7 = f (r 6 ); r 6 = 50 k to 1 m pin 7 i 7 1 20 a r -reference voltage c pins 6 and 3 v ref 1.06 1.13 1.18 v temperature coefficient pin 6 tc v ref 0.5 mv/k pulse output , see figure 20 pin 4 output pulse current r gt = 0, v gt = 1.2 v i o 100 155 190 ma reverse current i or 0.01 3.0 a output pulse width c j = 10 nf t p 80 s amplifier common-mode signal range pins 10 and 11 v 10 , 11 v 16 1 v input bias current pin 11 i io 0.01 1 a input offset voltage pins 10 and 11 v 10 10 mv output current pin 12 i o +i o 75 88 110 120 145 165 a a short circuit forward, transmittance see figure 16 i 12 = f(v 10 -11 ) pin 12 y f 1000 a/v pulse blocking, tacho monitoring pin 18 logic-on v ton 3.7 1.5 v logic-off v toff 1.25 1.0 v input current v 18 = v toff = 1.25 v v 18 = v 16 i i 14.5 0.3 1 a a output resistance r o 1.5 6 10 k
U211B2/ b3 rev. a2, 14-apr-98 11 (21) unit max. typ. min. symbol test conditions / pins parameters frequency-to-voltage converter pin 8 input bias current i ib 0.6 2 a input voltage limitation see figure 15 i i = 1 ma i i = +1 ma v i +v i 660 7.25 750 8.05 mv v turn-on threshold v ton 100 150 mv turn-off threshold v toff 20 50 mv charge amplifier discharge current see figure 2, c 5 = 1 nf, pin 9 i dis 0.5 ma charge transfer voltage pins 9 to 16 v ch 6.50 6.70 6.90 v charge transfer gain i 10 /i 9 pins 9 and 10 g i 7.5 8.3 9.0 conversion factor see figure 2 c 5 = 1 nf, r 6 = 100 k k 5.5 mv/hz output operating range pins 10 to 16 v o 0-6 v linearity 1 % soft-start, see figures 10, 11, 12, 13, 14 f/v-converter non-active starting current v 13 = v 16, v 8 = v 2 pin 13 i o 20 45 55 a final current v 13 = 0.5 pin 13 i o 50 85 130 a f/v-converter active starting current v 13 = v 16 pin 13 i o 2 4 7 a final current v 13 = 0.5 i o 30 55 80 a discharge current restart pulse pin 13 i o 0.5 3 10 ma automatic retriggering, see figure 21 pin 5 repetition rate r 5-3 = 0 t pp 3 4.5 6 t p p r 5-3 = 15 k t pp 20 t p load limiting, see figures 17, 18, 19 pin 14 operating voltage range pin 14 v i 1.0 1.0 v offset current v 10 = v 16 pin 14 v 14 = v 2 via 1 k pin 1516 i o 5 0.1 12 1.0 a input current v 10 = 4.5 v pin 14 i i 60 90 120 a output current v 14 = 300 mv pin 1516 i o 110 140 a overload on pin 1516 v ton 7.05 7.4 7.7 v
U211B2/ b3 rev. a2, 14-apr-98 12 (21) 0 0.2 0.4 0.6 0.8 0 80 120 160 200 240 phase angle ( ) r ( m ) 1.0 95 10302 10nf 4.7nf phase control reference point pin 2 2.2nf c /t =1.5nf figure 9. 02468 0 20 40 60 80 100 i ( a ) 13 v 13 ( v ) 10 95 10303 soft start f/v-converter non active reference point pin 16 figure 10. 02468 0 20 40 60 80 100 i ( a ) 13 v 13 ( v ) 10 95 10304 soft start f/v-converter active reference point pin 16 figure 11. 0 2 4 6 8 10 v ( v ) 13 t=f (c3) 95 10305 soft start f/v-converter non active reference point pin 16 figure 12. 0 2 4 6 8 10 v ( v ) 13 t=f (c3) 95 10306 soft start f/v-converter active reference point pin 16 figure 13. 0 2 4 6 8 10 v ( v ) 13 t=f (c3) 95 10307 soft start reference point pin 16 motor in action motor standstill ( dead time ) figure 14.
U211B2/ b3 rev. a2, 14-apr-98 13 (21) 10 8 6 4 2 500 250 0 250 500 i ( a ) 8 v 8 ( v ) 4 95 10308 02 reference point pin 2 f/vconverter figure 15. 300 200 100 0 200 100 50 0 50 100 i ( a ) 12 v 1011 ( v ) 300 95 10309 100 control amplifier reference point for i 12 = 4v figure 16. 024 6 0 50 100 150 200 i ( a) 1216 v 1516 ( v ) 8 95 10310 load limit control figure 17. 024 6 0 50 100 150 200 i ( a) 142 v 1016 (v) 8 95 10311 load limit control figure 18. 0 100 200 300 400 0 50 100 150 200 250 700 95 10312 500 600 i ( a ) 1516 v 142 ( mv ) i 15 =f ( v shunt ) v 10 =v 16 load current detection figure 19. 0 200 400 600 800 0 20 40 60 80 100 i ( ma ) gt r gt ( ) 1000 95 10313 pulse output v gt =0.8v 1.4v figure 20.
U211B2/ b3 rev. a2, 14-apr-98 14 (21) 0 6 12 18 24 0 5 10 15 20 r ( k ) 53 t pp /t p 30 95 10314 automatic retriggering figure 21. 04812 0 10 20 30 40 50 r ( k ) 1 i tot ( ma ) 16 95 10315 mains supply figure 22. 0102030 r 1 ( k ) 40 95 10316 mains supply 0 1 2 3 4 6 p ( w ) (r1) 5 figure 23. 03 6 9 12 0 1 2 3 4 6 p ( w ) (r1) i tot ( ma ) 15 95 10317 mains supply 5 figure 24.
U211B2/ b3 rev. a2, 14-apr-98 15 (21) 18 17 16 15 123 4 U211B2 14 13 12 56 7 11 8 10 9 r 3 m r 1 18 k d 1 220 k 470 k r 4 1.5 w 1n4004 180 r 12 22 25 v c 1 r 8 = 3 x 11 m r 10 2.2 k 230 v~ 680 pf c 5 r 2 1 m c 2 2.2 nf 1 k r 5 220 nf c 4 speed sensor r 7 15 k c 7 r 13 47 k 1 m r 11 c 6 100 nf r 6 100 k 220 nf c 8 2.2 10 v c 3 2.2 10 v c 10 250 k r 31 4.7 10 v c 9 470 k r 9 95 10364 gnd v s 1 w r 15 47 k r 16 47 k 10 k r 14 bzx55 set speed voltage l n t1 t2 2.2 / 10 v r c /t f f f f f c 11 2.2 f figure 25. speed control, automatic retriggering, load switch-off, soft-start the switch-off level at maximum load shows in principle the same speed dependency as the original version (see figure 2), but when reaching the maximum load, the motor is switched off completely. this function is effected by the thyristor (formed by t 1 and t 2) which ignites when the voltage at pin 15 reaches typ. 7.4 v (reference point pin 16). the circuit is thereby switched in the astand-by modeo over the release pin 18.
U211B2/ b3 rev. a2, 14-apr-98 16 (21) 18 17 16 15 1234 U211B2 14 13 12 567 11 8 10 9 r 3 m r 1 18 k d 1 220 k 470 k r 4 1.5 w 1n4004 180 r 12 22 25 v c 1 r 8 = 3 x 11 m r 10 2.2 k 230 v~ 680 pf c 5 r 2 1 m c 2 2.2 nf 1 k r 5 220 nf c 4 speed sensor r 7 15 k 2.2 / 10 v c 7 r 13 47 k 1 m r 11 c 6 100 nf r 6 100 k 220 nf c 8 2.2 10 v c 3 2.2 10 v c 10 250 k r 31 4.7 10 v 470 k r 9 gnd v s 1 w r 16 47 k r 15 33 k 10 k r 14 bzx55 set speed voltage l t1 t2 r c /t f f f f f 95 10366 n c 9 c 11 2.2 f figure 26. speed control, automatic retriggering, load switch-off, soft-start the maximum load regulation shows the principle in the same speed dependency as the original version (see figure 2). when reaching the maximum load, the control unit is turned to max , adjustable with r 2 . then only i o flows. this function is effected by the thyristor, formed by t 1 and t 2 which ignites as soon as the voltage at pin 15 reaches ca. 6.8 v (reference point pin 16). the potential at pin 15 is lifted and kept by r 14 over the internally operating threshold whereby the maximum load regulation starts and adjusts the control unit constantly to max (i o ), inspite of a reduced load current. the motor shows that the circuit is still in operation in the matter of a quiet buzzing sound.
U211B2/ b3 rev. a2, 14-apr-98 17 (21) 18 17 16 15 123 4 U211B2 14 13 12 56 7 11 8 10 9 r 3 m r 1 18 k d 1 220 k c 11 470 k r 4 1.5 w 1n4004 220 r 12 22 25 v c 1 r 8 = 3 x 11 m r 10 1 k 230 v~ 1 nf c 5 r 2 1 m c 2 2.2 nf 1 k r 5 220 nf c 4 speed sensor r 7 22 k c 7 r 13 47 k 1.5 m r 11 c 6 100 nf r 6 68 k 220 nf c 8 2.2 10 v c 3 2.2 10 v c 10 250 k r 31 4.7 c 9 1 m r 9 95 10365 gnd v s 1 w set speed voltage l n 1 /10 v 1 m 2.2 /10 v r c /t f f f f f f 22 nf figure 27. speed control, automatic retriggering, load limiting, soft-start, tacho control
U211B2/ b3 rev. a2, 14-apr-98 18 (21) 18 17 16 15 123 4 U211B2 14 13 12 56 7 11 8 10 9 22 nf r 4 m r 1 18 k d 1 220 k c 11 470 k r 5 1.5 w 1n4004 100 r 6 47 25 v c 1 230 v~ 680 pf c 6 r 2 1 m c 2 3.3 nf c 8 r 7 470 k 220 nf c 4 2.2 10 v c 3 4.7 10 v c 13 100 k r 31 95 10687 gnd v s 10 10 v r c /t r 11 c 7 16 k 470 nf set speed min r 18 set speed max r 13 47 k r 8 4.7 k r 3 r 9 220 k r 10 1.5 k 100 10 v c 10 c 5 470 nf cny 70 r 17 r 16 100 470 z 3 bzx55 c9v1 3.5 k / 8 w r 15 1n4004 d 2 i gt = 50 ma l 1 l 2 r 14 100 150 nf 250 v~ c 12 ca 220 pulses / revolution all diodes byw83 f f f f f figure 28. speed control with reflective opto coupler cny70 as emitter
U211B2/ b3 rev. a2, 14-apr-98 19 (21) 18 17 16 15 123 4 U211B2 14 13 12 56 7 11 8 10 9 22 nf r 3 m r 1 10 k d 1 110 k c 11 220 k r 4 1.1 w 1n4004 100 r 12 22 25 v c 1 230 v~ c 5 r 2 1 m c 2 3.3 nf c 7 r 11 820 k 470 nf c 6 2.2 10 v c 3 47 10 v c 10 220 k r 31 95 10688 gnd v s 10 r c /t r 7 c 8 16 k 470 nf set speed min r 14 set speed max r 13 82 k r 6 r 5 2.2 k cny 70 r 17 r 18 33 k 470 i gt = 50 ma 100 150 nf 250 v~ c 12 680 pf r 16 10 k c 4 1 nf 9 v 4.7 10 v c 9 r 9 220 k r 8 = 3 x 0.1 r 10 1.1 k c 13 1 f f f f f f figure 29. speed control, max. load control with reflective opto coupler cny70 as emitter
U211B2/ b3 rev. a2, 14-apr-98 20 (21) the circuit is designed as a speed control based on the reflection-coupled principle with 4 periods per revolution and a max. speed of 30.000 rpm. the separation of the coupler from the rotating aperture should be about 1 mm approximately. in this experimental circuit, the power supply for the coupler was provided externally because of the relatively high current consumption. instructions for adjusting: in the initial adjustment of the phase-control circuit, r 2 should be adjusted so that when r 14 = 0 and r 31 are in min. position, the motor just turns. the speed can now be adjusted as desired by means of r 31 between the limits determined by r 13 and r 14 . the switch-off power of the limiting-load control can be set by r 9 . the lower r 9 , the higher the switch-off power. package information 13019 package dip18 dimensions in mm 0.5 min technical drawings according to din specifications 7.77 7.47 23.3 max 4.8 max 3.3 6.4 max 0.36 max 9.8 8.2 1.64 1.44 0.58 0.48 2.54 20.32 18 10 19 13036 technical drawings according to din specifications package so16 dimensions in mm 10.0 9.85 8.89 0.4 1.27 1.4 0.25 0.10 5.2 4.8 3.7 3.8 6.15 5.85 0.2 16 9 18
U211B2/ b3 rev. a2, 14-apr-98 21 (21) ozone depleting substances policy statement it is the policy of temic telefunken microelectronic gmbh to 1. meet all present and future national and international statutory requirements. 2. regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. it is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances ( odss). the montreal protocol ( 1987) and its london amendments ( 1990) intend to severely restrict the use of odss and forbid their use within the next ten years. various national and international initiatives are pressing for an earlier ban on these substances. temic telefunken microelectronic gmbh semiconductor division has been able to use its policy of continuous improvements to eliminate the use of odss listed in the following documents. 1. annex a, b and list of transitional substances of the montreal protocol and the london amendments respectively 2 . class i and ii ozone depleting substances in the clean air act amendments of 1990 by the environmental protection agency ( epa ) in the usa 3. council decision 88/540/eec and 91/690/eec annex a, b and c ( transitional substances ) respectively. temic can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances. we reserve the right to make changes to improve technical design and may do so without further notice . parameters can vary in different applications. all operating parameters must be validated for each customer application by the customer. should the buyer use temic products for any unintended or unauthorized application, the buyer shall indemnify temic against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. temic telefunken microelectronic gmbh, p.o.b. 3535, d-74025 heilbronn, germany telephone: 49 ( 0 ) 7131 67 2831, fax number: 49 ( 0 ) 7131 67 2423

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